VFC320 VFC 320 SBVS017A - AUGUST 2001 Voltage-to-Frequency and Frequency-to-Voltage CONVERTER FEATURES DESCRIPTION HIGH LINEARITY: 12 to 14 bits 0.005% max at 10kHz FS 0.03% max at 100kHz FS 0.1% typ at 1MHz FS V/F OR F/V CONVERSION 6-DECADE DYNAMIC RANGE GAIN DRIFT: 20ppm/C max OUTPUT TTL/CMOS COMPATIBLE The VFC320 monolithic voltage-to-frequency and frequency-tovoltage converter provides a simple low cost method of converting analog signals into digital pulses. The digital output is an open collector and the digital pulse train repetition rate is proportional to the amplitude of the analog input voltage. Output pulses are compatible with TTL, and CMOS logic families. High linearity (0.005%, max at 10kHz FS) is achieved with relatively few external components. Two external resistors and two external capacitors are required to operate. Full scale frequency and input voltage are determined by a resistor in series with -In and two capacitors (one-shot timing and input amplifier integration). The other resistor is a non-critical open collector pull-up (fOUT to +VCC). The VFC320 is available in two performance grades. The VFC320 is specified for the -25C to +85C, range. APPLICATIONS INEXPENSIVE A/D AND D/A CONVERTER DIGITAL PANEL METERS TWO-WIRE DIGITAL TRANSMISSION WITH NOISE IMMUNITY FM MOD/DEMOD OF TRANSDUCER SIGNALS PRECISION LONG TERM INTEGRATOR HIGH RESOLUTION OPTICAL LINK FOR ISOLATION AC LINE FREQUENCY MONITOR MOTOR SPEED MONITOR AND CONTROL +VCC VOUT fIN -In +In Comparators -7.5V Ref Flipflop fOUT One-shot -VCC C1 Common Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. Copyright (c) 1982, Texas Instruments Incorporated PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. www.ti.com ELECTRICAL CHARACTERISTICS At TA = +25C and 15VDC power supply, unless otherwise noted. VFC320BP PARAMETER CONDITIONS MIN Fig. 4 with e2 = 0 Fig. 4 with e1 = 0 IIN = VIN/RIN >0 <0 +0.25 TYP VFC320CP MAX MIN TYP MAX UNITS V V A V/F CONVERTER fOUT = VIN/7.5 R1C1, Figure 4 INPUT TO OP AMP Voltage Range(1) Current Range(1) Bias Current Inverting Input Noninverting Input Offset Voltage(3) Offset Voltage Drift Differential Impedance Common-Mode Impedance ACCURACY Linearity Error (1) (4) (5) Offset Error Input Offset Voltage(3) Offset Drift(7) Gain Error(3) Gain Drift(7) Full Scale Drift (Offset Drift and Gain Drift) (7)(8)(9) Power Supply Sensitivity DYNAMIC RESPONSE Full Scale Frequency Dynamic Range Settling Time Overload Recovery OPEN COLLECTOR OUTPUT Voltage, Logic "0" Leakage Current, Logic "1" Voltage, Logic "1" Duty Cycle at FS Fall Time Note 2 -10 +750 4 10 300 || 5 5 650 || 5 300 || 3 500 || 3 Fig. 4 with e2 = 0(6) 0.01Hz fOUT 10kHz 0.1Hz fOUT 100kHz 1Hz fOUT 1MHz 0.004 0.008 0.1 0.5 5 8 30 0.15 k || pF 0.0015 15 10 50 50 VCC = 14VDC to 18VDC 0.015 1 % FSR % FSR % FSR 20 20 ppm FSR ppm FSR/C % FSR ppm FSR/C ppm FSR/C % FSR% MHz Decades V A V % ns Note 10 Note 10 ISINK = 8mA, max VO = 15V External Pull-up Resistor Required (See Figure 4) For Best Linearity IOUT = 5mA, CLOAD = 500pF 0.002 6 (V/F) to Specified Linearity For a Full Scale Input Step <50% Overload nA nA mV V/C k || pF 0.005 0.030 f = 10kHz f = 10kHz CLOAD 50pF 0.01 0.4 1.0 VPU 25 100 F/V CONVERTER VOUT = 7.5 R1C1 fIN, Figure 9 INPUT TO COMPARATOR Impedance Logic "1" Logic "0" Pulse-width Range OUTPUT FROM OP AMP Voltage Current Impedance Capacitive Load POWER SUPPLY Rated Voltage Voltage Range Quiescent Current TEMPERATURE RANGE Specification B and C Grades S Grade Operating B and C Grades S Grade Storage 50 || 10 +1.0 -VCC 0.25 IO = 6mA VO = 7VDC Closed-Loop Without Oscillation 150 || 10 +VCC -0.05 0 to +10 +10 0.1 100 13 15 k || pF V V s V mA pF V V mA 20 7.5 -25 -55 +85 +125 C C -40 -55 -65 +85 +125 +150 C C C 6.5 Specification the same as for VFC320BP. NOTES: (1) A 25% duty cycle at full scale (0.25mA input current) is recommended where possible to achieve best linearity. (2) Determined by RIN and full scale current range constraints. (3) Adjustable to zero. See Offset and Gain Adjustment section. (4) Linearity error at any operating frequency is defined as the deviation from a straight line drawn between the full scale frequency and 0.1% of full scale frequency. See Discussion of Specifications section. (5) When offset and gain errors are nulled, at an operating temperature, the linearity error determines the final accuracy. (6) For e1 = 0 typical linearity errors are: 0.01% at 10kHz, 0.2% at 100kHz, 0.1% at 1MHz. (7) Exclusive of external components' drift. (8) FSR = Full Scale Range (corresponds to full scale and full scale input voltage.) (9) Positive drift is defined to be increasing frequency with increasing temperature. (10) One pulse of new frequency plus 50ns typical. 2 VFC320 SBVS017A ABSOLUTE MAXIMUM RATINGS ELECTROSTATIC DISCHARGE SENSITIVITY Supply Voltage ................................................................................... 20V Output Sink Current at fOUT ............................................................... 50mA Output Current at VOUT ................................................................... +20mA Input Voltage, -Input .......................................................................... VCC Input Voltage, +Input .......................................................................... VCC Storage Temperature Range .......................................... -65C to +150C Lead Temperature (soldering, 10s) ............................................... +300C This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. PACKAGE/ORDERING INFORMATION PRODUCT PACKAGE PACKAGE DRAWING NUMBER PACKAGE DESIGNATOR SPECIFIED TEMPERATURE RANGE VFC320BP DIP-14 010 N -40C to +85C VFC320CP DIP-14 010 N -40C to +85C PACKAGE MARKING ORDERING NUMBER(1) TRANSPORT MEDIA NOTE: (1) Models with a slash (/) are available only in Tape and Reel in the quantities indicated (e.g., /2K5 indicates 2500 devices per reel). Ordering 2500 pieces of "VFC320BP/2K5" will get a single 2500-piece Tape and Reel. PIN CONFIGURATION Top View VFC320 SBVS017A DIP -In 1 14 +In NC 2 13 VOUT NC 3 -VCC 4 One-Shot Capacitor 5 NC 6 fOUT 7 Input Amp 12 +VCC Switch 11 Common Oneshot 10 Comparator Input 9 NC 8 NC 3 DISCUSSION OF SPECIFICATIONS FREQUENCY STABILITY VS TEMPERATURE Linearity is the maximum deviation of the actual transfer function from a straight line drawn between the end points (100% full scale input or frequency and 0.1% of full scale called zero.) Linearity is the most demanding measure of voltage-to-frequency converter performance, and is a function of the full scale frequency. Refer to Figure 1 to determine typical linearity error for your application. Once the full scale frequency is chosen, the linearity is a function of operating frequency as it varies between zero and full scale. Examples for 10kHz full scale are shown in Figure 2. Best linearity is achieved at lower gains (fOUT/VIN) with operation as close to the chosen full scale frequency as possible The high linearity of the VFC320 makes the device an excellent choice for use as the front end of Analog-to-Digital (A/D) converters with 12- to 14-bit resolution, and for highly accurate transfer of analog data over long lines in noisy environments (2-wire digital transmission.) 1000 Typical Full Scale Temp Drift (ppm of FSR/C) LINEARITY The full scale frequency drift of the VFC320 versus temperature is expressed as parts per million of full scale range per C. As shown in Figure 3, the drift increases above 10kHz. To determine the total accuracy drift over temperature, the drift coefficients of external components (especially R1 and C1) must be added to the drift of the VFC320. 100 B and S Grades C Grade 10 1k 10k 100k 1M Full Scale Frequency (Hz) Figure 3. Full Scale Drift vs Full Scale Frequency. Typical Linearity Error (% of FSR) 0.10 RESPONSE Response of the VFC320 to changes in input signal level is specified for a full scale step, and is 50ns plus 1 pulse of the new frequency. For a 10V input signal step with the VFC320 operating at 100kHz full scale, the settling time to within 0.01% of full scale is 10s. 0.01 TA = +25C DFS = 0.25 THEORY OF OPERATION 0.001 1k 10k 100k 1M Full Scale Frequency (Hz) Figure 1. Linearity Error vs Full Scale Frequency. Figure Typical Linearity jErrorf (% of FSR) 0.003 fFULL SCALE = 10kHz 0.002 B Grade 0.001 C Grade 0 -0.001 -0.002 Typical, TA = +25C -0.003 0 1k 2k 3k 4k 5k 6k 7k 8k Operating Frequency (Hz) Figure 2. Linearity Error vs Operating Frequency. Figure 4 9k 10k The VFC320 monolithic voltage-to-frequency converter provides a digital pulse train output whose repetition rate is directly proportional to the analog input voltage. The circuit shown in Figure 4 is composed of an input amplifier, two comparators and a flip-flop (forming a on-shot), two switched current sinks, and an open collector output transistor stage. Essentially the input amplifier acts as an integrator that produces a two-part ramp. The first part is a function of the input voltage, and the second part is dependent on the input voltage and current sink. When a positive input voltage is applied at VIN, a current will flow through the input resistor, causing the voltage at VOUT to ramp down toward zero, according to dV/dt = VIN/R1C1. During this time the constant current sink is disabled by the switch. Note, this period is only dependent on VIN and the integrating components. When the ramp reaches a voltage close to zero, comparator A sets the flip-flop. This closes the current sink switches as well as changing fOUT from logic 0 to logic 1. The ramp now begins to ramp up, and 1mA charges through C1 until VC1 = -7.5V. Note this ramp period is dependent on the 1mA current sink, connected to the negative input of the op amp, as well as the input voltage. At this -7.5V threshold point C1, comparator B resets the flip-flop, and the ramp voltage VFC320 SBVS017A C2 Input Resistor R1 IIN e1 +VPULL-UP (VPU) (5V to 15V Typically) +VCC Integrating Capacitor VOUT 13 10 fIN 12 1 Input Amp 14 IB IA e2 Pull-up Resitor A Comparators -7.5V Ref Constant Current Sinks (1mA) R2 7 Flipflop fOUT Q1 B fOUT = Switch VIN 7.5 R1 C1 One-shot 4 -VCC 5 C1 11 Common One-shot Capacitor VIN: For Postive Input Voltages use e1, short e2. For Negative Input Voltages use e2, short e1. For Differental Input Voltages use e1 and e2. FIGURE 4. Functional Block Diagram of the VFC320. begins to ramp down again before the input amplifier has a chance to saturate. In effect the comparators and flip-flop form a one-shot whose period is determined by the internal reference and a 1mA current sink plus the external capacitor, C1. After the one-shot resets, fOUT changes back to logic 0 and the cycle begins again. The transfer function for the VFC320 is derived for the circuit shown in Figure 4. Detailed waveforms are shown in Figure 5. fOUT = 1 (1) t1 + t2 One-shot VC1 0V Thus Q = 0 = IIN t1 + (IIN - IA) t2 (2) So that IIN (t1 + t2) = IA t2 (3) But since t1 + t2 = fOUT = 1 fOUT and IIN = VIN R1 VIN (4), (5) (6) IA R2 R2 In the time t1, IB charges the one-shot capacitor C1 until its voltage reaches -7.5V and trips comparator B. CIN 7.5 Thus t2 = (7) IB Using (7) in (6) yield fOUT = Since IA = IB the result is VIN fOUT = 7.5 R C -7.5V 1 VIN I * B 7.5R1C1 I A (8) (9) 1 VOUT t1 t2 VFC Output fOUT Integrator Output VOUT In the time t1 + t2 the integrator capacitor C2 charges and discharges but the net voltage change is zero. Since the integrating capacitor, C2, affects both the rising and falling segments of the ramp voltage, its tolerance and temperature coefficient do not affect the output frequency. It should, however, have a leakage current that is small compared to IIN, since this parameter will add directly to the gain error of the VFC. C1, which controls the one-shot period, should be very precise since its tolerance and temperature coefficient add directly to the errors in the transfer function. FIGURE 5. Integrator and VFC Output Timing. VFC320 SBVS017A 5 The operation of the VFC320 as a highly linear frequencyto-voltage converter, follows the same theory of operation as the voltage-to-frequency converter. e1 and e2 are shorted and FIN is disconnected from VOUT. FIN is then driven with a signal which is sufficient to trigger comparator A. The oneshot period will then be determined by C1 as before, but the cycle repetition frequency will be dictated by the digital input at FIN. C2 Gain Adjustment IIN 1 R1 NC 2 +15V R4 D FS = t2 = PW * fFS t1 + t 2 NC 3 VIN max / R1 = IIN max 1mA 1mA Thus DFS = 0.25 corresponds to IIN max = 0.25mA. INSTALLATION AND OPERATING INSTRUCTIONS VOLTAGE-TO-FREQUENCY CONVERSION The VCF320 can be connected to operate as a V/F converter that will accept either positive or negative input voltages, or an input current. Refer to Figures 6 and 7. C2 Integrator Capacitor Gain Adjustment 1 14 R1 NC 2 +15V R4 13 Input Amp NC 3 R5 -VCC(1) 4 -15V Offset Adj. 5 NC 6 10 +VPU Oneshot 7 R2 fOUT NOTE: (1) Bypass with 0.01F 9 NC 8 NC Pin numbers in squares refer to DIP package. FIGURE 6. Connection Diagram for V/F Conversion, Positive Input Voltages. 6 Switch 10 NC 6 +VPU Oneshot 7 R2 fOUT NOTE: (1) Bypass with 0.01F 9 NC 8 NC Pin numbers in squares refer to DIP package. EXTERNAL COMPONENT SELECTION In general, the design sequence consists of: (1) choosing fMAX, (2) choosing the duty cycle at full scale (DFS = 0.25 typically), (3) determining the input resistor, R1 (Figure 4), (4) calculating the one-shot capacitor, C1, (5) selecting the integrator capacitor C2, and (6) selecting the output pull-up resistor, R2. Input Resistors R1 and R3 The input resistance (R1 and R3 in Figures 6 and 7) is calculated to set the desired input current at full scale input voltage. This is normally 0.25mA to provide a 25% duty cycle at full scale input and output. Values other than DFS = 0.25 may be used but linearity will be affected. The nominal value is R1 is VINmax R1 = 0.25mA One-Shot Capacitor, C1 C1 One-shot capacitor 5 C1 One-shot Capacitor 12 +VCC(1) 11 Switch R3 11 (10) If gain trimming is to be done, the nominal value is reduced by the tolerance of C1 and the desired trim range. R1 should have a very-low temperature coefficient since its drift adds directly to the errors in the transfer function. IIN VIN -15V Offset Adj. 12 +VCC(1) FIGURE 7. Connection Diagram for V/F Conversion, Negative Input Voltages. Best linearity is achieved when DFS is 25%. By reducing equations (7) and (9) it can be shown that DFS = 13 Input Amp -VCC(1) 4 The duty cycle (D) of the VFC is the ratio of the one-shot period (t2) or pulse width, PW, to the total VFC period (t1 + t2). For the VFC320, t2 is fixed and t1 + t2 varies as the input voltage. Thus the duty cycle, D, is a function of the input voltage. Of particular interest is the duty cycle at full scale frequency, DFS, which occurs at full scale input. DFS is a user determined parameter which affects linearity. VIN 14 R3 R5 DUTY CYCLE Integrator Capacitor This capacitor determines the duration of the one-shot pulse. From equation (9) the nominal value is VIN C1 NOM = 7.5 R1 fOUT (11) For the usual 25% duty at fMAX = VIN/R1 = 0.25mA there is approximately 15pF of residual capacitance so that the design value is C1(pF) = 33 * 10 6 fFS - 15 (12) VFC320 SBVS017A where fFS is the full scale output frequency in Hz. The temperature drift of C1 is critical since it will add directly to the errors of the transfer function. An NPO ceramic type is recommended. Every effort should be made to minimize stray capacitance associated with C1. It should be mounted as close to the VFC320 as possible. Figure 8 shows pulse width and full scale frequency for various values of C1 at DFS = 25%. 105 100 104 Pulse Width 103 10 102 1 10 Full Scale Frequency (Hz) Pulse Width (s) Full Scale Frequency 1000 1 10 2 3 10 10 4 To null errors to zero, follow this procedure: 1. Apply an input voltage that should produce an output frequency of 0.001 * full scale. 2. Adjust R5 for proper output. 3. Apply the full scale input voltage. 4. Adjust R3 for proper output. 5. Repeat stems 1 through 4. If nulling is unnecessary for the application, delete R4 and R5, and replace R3 with a short circuit. 106 10,000 OFFSET AND GAIN ADJUSTMENT PROCEDURES 5 10 Capacitance C1(pF) FIGURE 8. Output Pulse Width (DFS = 0.25) and Full Scale Frequency vs External One-shot Capacitance. POWER SUPPLY CONSIDERATIONS The power supply rejection ratio of the VFC320 is 0.015% of FSR/% max. To maintain 0.015% conversion, power supplies which are stable to within 1% are recommended. These supplies should be bypassed as close as possible to the converter with 0.01F capacitors. Internal circuitry causes some current to flow in the common connection (pin 11 on DIP package). Current flowing into the fOUT pin (logic sink current) will also contribute to this current. It is advisable to separate this common lead ground from the analog ground associated with the integrator input to avoid errors produced by these currents flowing through any ground return impedance. Integrating Capacitor, C2 Since C2 does not occur in the V/F transfer function equation (9), its tolerance and temperature stability are not important; however, leakage current in C2 causes a gain error. A ceramic type is sufficient for most applications. The value of C2 determines the amplitude of VOUT. Input amplifier saturation, noise levels for the comparators and slew rate limiting of the integrator determine a range of acceptable values, 100/fFS; if fFS 100kHz C2 (F) = (13) 0.001; if 100kHz < fFS 500kHz 0.0005; if fFS > 500kHz Output Pull Up Resistor R2 The open collector output can sink up to 8mA and still be TTL-compatible. Select R2 according to this equation: R2 min () VPULLUP/(8mA - ILOAD) A 10% carbon film resistor is suitable for use as R2. DESIGN EXAMPLE Given a full scale input of +10V, select the values of R1, R2, R3, C1, and C2 for a 25% duty cycle at 100kHz maximum operation into one TTL load. See Figure 6. Selecting C1 (DFS = 0.25) C1 = [(33 * 106)/fMAX] - 15 if DFS = 0.5 = [(33 * 106)/100kHz] - 15 = 315pF Choose a 300pF NPO ceramic capacitor with 1% to 10% tolerance. Selecting R1 and R3 (DRS = 0.25) R1 + R3 = VIN max/0.25mA VIN max/0.5mA if DFS = 0.5 Trimming Components R3, R4, R5 = 10V/0.25mA R5 nulls the offset voltage of the input amplifier. It should have a series resistance between 10k and 100k and a temperature coefficient less than 100ppm/C. R4 can be a 10% carbon film resistor with a value of 10M. = 40k R3 nulls the gain errors of the converter and compensates for initial tolerances of R1 and C1. Its total resistance should be at least 20% of R1, if R1 is selected 10% low. Its temperature coefficient should be no greater than five times that of R1 to maintain a low drift of the R3 - R1 series combination. [(66 * 106)/fMAX] - 15 Choose 32.4k metal film resistor with 1% tolerance and R3 = 10k cermet potentiometer. Selecting C2 C2 = 102/FMAX = 102/100kHz = 0.001F Choose a 0.001F capacitor with 5% tolerance. VFC320 SBVS017A 7 Selecting R2 pin 10 should be biased closer to zero to insure that the input signal at pin 10 crosses the zero threshold. R2 = VPULLUP/(8mA - ILOAD) Errors are nulled using 0.001 * full scale frequency to null offset, and full scale frequency to null the gain error. The procedure is given on this page. Use equations from V/F calculations to find R1, R3, R4, C1 and C2. =5V/(8mA - 1.6mA), one TTL-load = 1.6mA =781 Choose a 750 1/4-watt carbon compensation resistor with 5% tolerance. TYPICAL APPLICATIONS FREQUENCY-TO-VOLTAGE CONVERSION To operate the VFC320 as a frequency-to-voltage converter, connect the unit as shown in Figure 9. To interface with TTL-logic, the input should be coupled through a capacitor, and the input to pin 10 biased near +2.5V. The converter will detect the falling edges of the input pulse train as the voltage at pin 10 crosses zero. Choose C3 to make t = 0.1t (see Figure 9). For input signals with amplitudes less than 5V, Excellent linearity, wide dynamic range, and compatible TTL, DTL, and CMOS digital output make the VFC320 ideal for a variety of VFC applications. High accuracy allows the VFC320 to be used where absolute or exact readings must be made. It is also suitable for systems requiring high resolution up to 14 bits Figures 10-14 show typical applications of the VFC320. R1 R3 C2 +15V Integrator Capacitor R4 R5 1 14 NC 2 13 T -15V Input Amp NC 3 One-shot Capacitor 11 Switch -VCC(1) 4 12 5 10 +VCC(1) 12k 2.5V C1 NC 6 fOUT Oneshot 7 NOTE: (1) Bypass with 0.01F 9 NC 8 NC Pin numbers in squares refer to DIP package. VOUT R6 +1V 0V C3 (t) fIN 0.001F R7 2.2k FFS = 100kHz FIGURE 9. Connection Diagram for F/V Conversion. + Sensor INA101 VIN fOUT Counter VFC320 - High Noise Immunity Instrumentation Amp Parallel Data Computer Clock FIGURE 10. Inexpensive A/D with Two-Wire Digital Transmission Over Twisted Pair. e1 Differential e2 Input VIN VFC320 fOUT BDC Counter Clock Driver/Display FIGURE 11. Inexpensive Digital Panel Meter. 8 VFC320 SBVS017A fIN VFC320 VOUT F/V Digital Output VIN INA101 Transducer VFC320 V/F fOUT FOT Analog Output BCD Counter FOR 0.005% Linearity Precision DC levels down to 10mV full scale Driver Instrumentation Amp Clock Display FIGURE 12. Remote Transducer Readout via Fiber Optic Link (Analog and Digital Output). +15V Gain Adjust +10V to -10V Input 8 0.01F R1 11k D1 IN4154 30k 7 +15V 1 20k 20k REF101 4 6 10V 12 1 2k 10 11 7 14 5 3 Integrator Current C2 R4 3510B 8.66k e1 Bipolar Input 13 VFC320 5 R3 40.2k R2 100k VIN + fOUT VFC320 Q1 C1 3270pF 2N2222 0 to 10kHz Output 0.01F - Sign Bit Out 4.7k 4.7k 3300pF -15V FIGURE 13. Bipolar input is accomplished by offsetting the input to the VFC with a reference voltage. Accurately matched resistors in the REF101 provide a stable half-scale output frequency at zero volts input. VFC320 SBVS017A +VCC FIGURE 14. Absolute value circuit with the VFC320. Op amp, D1 and Q1 (its base-emitter junction functioning as a diode) provide full-wave rectification of bipolar input voltages. VFC output frequency is proportional to | e1 |. The sign bit output provides indication of the input polarity. 9 PACKAGE DRAWING MPDI002B - JANUARY 1995 - REVISED FEBRUARY 2000 N (R-PDIP-T**) PLASTIC DUAL-IN-LINE PACKAGE 16 PINS SHOWN PINS ** 14 16 18 20 A MAX 0.775 (19,69) 0.775 (19,69) 0.920 (23,37) 0.975 (24,77) A MIN 0.745 (18,92) 0.745 (18,92) 0.850 (21,59) 0.940 (23,88) DIM A 16 9 0.260 (6,60) 0.240 (6,10) 1 8 0.070 (1,78) MAX 0.035 (0,89) MAX 0.325 (8,26) 0.300 (7,62) 0.020 (0,51) MIN 0.015 (0,38) Gauge Plane 0.200 (5,08) MAX Seating Plane 0.010 (0,25) NOM 0.125 (3,18) MIN 0.100 (2,54) 0.021 (0,53) 0.015 (0,38) 0.430 (10,92) MAX 0.010 (0,25) M 14/18 PIN ONLY 4040049/D 02/00 NOTES: A. All linear dimensions are in inches (millimeters). B. This drawing is subject to change without notice. C. Falls within JEDEC MS-001 (20-pin package is shorter than MS-001). 10 VFC320 SBVS017A IMPORTANT NOTICE Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, modifications, enhancements, improvements, and other changes to its products and services at any time and to discontinue any product or service without notice. Customers should obtain the latest relevant information before placing orders and should verify that such information is current and complete. All products are sold subject to TI's terms and conditions of sale supplied at the time of order acknowledgment. TI warrants performance of its hardware products to the specifications applicable at the time of sale in accordance with TI's standard warranty. Testing and other quality control techniques are used to the extent TI deems necessary to support this warranty. Except where mandated by government requirements, testing of all parameters of each product is not necessarily performed. TI assumes no liability for applications assistance or customer product design. Customers are responsible for their products and applications using TI components. To minimize the risks associated with customer products and applications, customers should provide adequate design and operating safeguards. TI does not warrant or represent that any license, either express or implied, is granted under any TI patent right, copyright, mask work right, or other TI intellectual property right relating to any combination, machine, or process in which TI products or services are used. Information published by TI regarding third-party products or services does not constitute a license from TI to use such products or services or a warranty or endorsement thereof. Use of such information may require a license from a third party under the patents or other intellectual property of the third party, or a license from TI under the patents or other intellectual property of TI. Reproduction of TI information in TI data books or data sheets is permissible only if reproduction is without alteration and is accompanied by all associated warranties, conditions, limitations, and notices. Reproduction of this information with alteration is an unfair and deceptive business practice. TI is not responsible or liable for such altered documentation. Information of third parties may be subject to additional restrictions. Resale of TI products or services with statements different from or beyond the parameters stated by TI for that product or service voids all express and any implied warranties for the associated TI product or service and is an unfair and deceptive business practice. TI is not responsible or liable for any such statements. TI products are not authorized for use in safety-critical applications (such as life support) where a failure of the TI product would reasonably be expected to cause severe personal injury or death, unless officers of the parties have executed an agreement specifically governing such use. Buyers represent that they have all necessary expertise in the safety and regulatory ramifications of their applications, and acknowledge and agree that they are solely responsible for all legal, regulatory and safety-related requirements concerning their products and any use of TI products in such safety-critical applications, notwithstanding any applications-related information or support that may be provided by TI. Further, Buyers must fully indemnify TI and its representatives against any damages arising out of the use of TI products in such safety-critical applications. TI products are neither designed nor intended for use in military/aerospace applications or environments unless the TI products are specifically designated by TI as military-grade or "enhanced plastic." Only products designated by TI as military-grade meet military specifications. Buyers acknowledge and agree that any such use of TI products which TI has not designated as military-grade is solely at the Buyer's risk, and that they are solely responsible for compliance with all legal and regulatory requirements in connection with such use. TI products are neither designed nor intended for use in automotive applications or environments unless the specific TI products are designated by TI as compliant with ISO/TS 16949 requirements. Buyers acknowledge and agree that, if they use any non-designated products in automotive applications, TI will not be responsible for any failure to meet such requirements. Following are URLs where you can obtain information on other Texas Instruments products and application solutions: Products Amplifiers Data Converters DSP Clocks and Timers Interface Logic Power Mgmt Microcontrollers RFID RF/IF and ZigBee(R) Solutions amplifier.ti.com dataconverter.ti.com dsp.ti.com www.ti.com/clocks interface.ti.com logic.ti.com power.ti.com microcontroller.ti.com www.ti-rfid.com www.ti.com/lprf Applications Audio Automotive Broadband Digital Control Medical Military Optical Networking Security Telephony Video & Imaging Wireless www.ti.com/audio www.ti.com/automotive www.ti.com/broadband www.ti.com/digitalcontrol www.ti.com/medical www.ti.com/military www.ti.com/opticalnetwork www.ti.com/security www.ti.com/telephony www.ti.com/video www.ti.com/wireless Mailing Address: Texas Instruments, Post Office Box 655303, Dallas, Texas 75265 Copyright (c) 2008, Texas Instruments Incorporated